Welcome to the course Antennas, Arrays, & Metasurfaces (ARM)
Lectures and notes
Review content
-
Review of Maxwell’s equations, phasor notation, plane wave propagation in free space and dielectric media, polarization, multipath. 19, 20 Jan 2026 — Ch 1 of AE,ME
notesReview Questions: Wave Propagation, Polarization, and Attenuation
-
[Level 1] What is the relationship between the electric field \(\vec{E}\) and magnetic field \(\vec{H}\) for a plane wave propagating in free space? State the characteristic impedance of free space.
Answer:
For a plane wave in free space, \(\vec{H} = (1/\eta_0) \hat{k} \times \vec{E}\), where \(\hat{k}\) is the unit vector in the direction of propagation and \(\eta_0 = \sqrt{\mu_0/\varepsilon_0} = 120\pi \approx 377\ \Omega\) is the characteristic impedance (or intrinsic impedance) of free space. The fields are perpendicular to each other and to the direction of propagation, forming a right-handed coordinate system.
-
[Level 2] Explain the difference between forward and backward traveling waves in the phasor domain. How do you identify the direction of propagation from the phase term?
Answer:
A forward traveling wave has the form \(e^{-jk_0z}\) (propagating in +z direction), while a backward traveling wave has the form \(e^{+jk_0z}\) (propagating in -z direction). The direction is identified by examining the phase term: for constant phase \(\omega t - k_0z = \text{const}\), as time increases, z must also increase (forward wave). For \(\omega t + k_0z = \text{const}\), as time increases, z must decrease (backward wave).
-
[Level 2] What are the three types of polarization for electromagnetic waves? Describe the condition for each type.
Answer:
-
Linear polarization: Phase difference \(\delta = 0\), the electric field vector oscillates along a fixed direction (\(\vec{E} = (a_x, 0, 0)\) or \((0, a_y, 0)\) or superposition with \(\delta = 0\))
-
Circular polarization: Phase difference \(\delta = \pm\pi/2\) and equal amplitudes \(a_x = a_y = a\). The magnitude \(|\vec{E}|\) remains constant in time and the vector rotates. \(\delta = -\pi/2\) gives right circular, \(\delta = +\pi/2\) gives left circular.
-
Elliptical polarization: Any other case - general phase difference or unequal amplitudes.
-
-
[Level 3] A wave propagates in a lossy medium with complex permittivity \(\varepsilon = \varepsilon' - j\varepsilon"\). Calculate the skin depth (in meters) for a wave at 10 GHz propagating in a material with \(\varepsilon_r = 4\) and loss tangent \(\tan \delta = 0.1\). Assume free-space permeability \(\mu = \mu_0\).
Answer:
The complex wave vector is \(k = k_0\sqrt{\varepsilon_r(1 - j \tan \delta)} = k_r - jk_i\). For small loss, \(k_i \approx (k_0\sqrt{\varepsilon_r} \tan \delta)/2\). With \(f = 10\) GHz, \(k_0 = 2\pi f/c = 2\pi \times 10^{10}/(3 \times 10^8) = 209.4\) rad/m. Then \(k_i \approx (209.4 \times 2 \times 0.1)/2 = 20.94\) rad/m. The skin depth is \(\delta_s = 1/k_i = 1/20.94 \approx\) 0.048 m or 4.8 cm.
-
[Level 4] Consider a multipath scenario where a transmitter sends a right-hand circularly polarized (RHCP) wave that reflects off a ground plane with reflection coefficients \(R_H = -0.8\angle 10°\) and \(R_V = -0.6\angle -15°\) for horizontal and vertical polarizations respectively. Will the reflected wave be circularly polarized? Justify your answer quantitatively.
Answer:
No, the reflected wave will be elliptically polarized. An RHCP wave can be decomposed as \(\vec{E}_{inc} = (E_0/\sqrt{2})(1, -j, 0)e^{-jkz}\). After reflection, the H and V components are scaled differently:
-
H-component: \(E_{H,refl} = R_H \times E_0/\sqrt{2} = -0.8\angle 10° \times E_0/\sqrt{2}\)
-
V-component: \(E_{V,refl} = R_V \times (-j)E_0/\sqrt{2} = -0.6\angle -15° \times E_0/\sqrt{2} \angle -90°\)
The reflected wave has:
-
Different magnitudes: \(|E_{H,refl}| = 0.8E_0/\sqrt{2} \neq |E_{V,refl}| = 0.6E_0/\sqrt{2}\) (equal magnitude required for circular polarization violated)
-
Phase difference: \(\Delta\phi = 10° - (-15° - 90°) = 10° + 105° = 115°\) (not \(\pm 90°\) required for circular polarization)
Therefore, the reflected wave is elliptically polarized with axial ratio \(AR = 0.8/0.6 = 1.33\) (or 2.5 dB).
-
Exploration Topics: Historical Context & Modern Applications
1. Maxwell’s Prediction and Hertz’s Verification (1865-1888)
James Clerk Maxwell unified electricity and magnetism in his 1865 equations, predicting electromagnetic waves travel at the speed of light. Heinrich Hertz experimentally verified this in 1888, generating and detecting radio waves for the first time.
Research: How did Hertz’s spark gap transmitter and loop antenna detector work? What was the wavelength of his first transmitted waves?
2. Polarization in Modern Communication Systems
Polarization diversity is exploited in modern systems:
-
Satellite communications: Dual-polarized antennas (H/V or LHCP/RHCP) double channel capacity
-
Weather radar: Dual-polarization distinguishes rain from hail by analyzing differential reflectivity
-
5G MIMO: Cross-polarized antenna arrays reduce correlation and increase capacity
Investigate: Why does GPS use RHCP? How do polarization-maintaining optical fibers work?
3. Millimeter Wave Propagation and 5G Challenges
The high attenuation you calculated (4.8 cm skin depth at 10 GHz) becomes critical for mmWave 5G (24-100 GHz). Rain attenuation at 60 GHz can exceed 15 dB/km, and oxygen absorption creates a peak at 60 GHz.
Explore: Why is the 60 GHz band both a challenge and opportunity? How do massive MIMO and beamforming overcome mmWave propagation losses?
4. Atmospheric Propagation Windows
The atmosphere has "windows" where EM waves propagate with minimal attenuation, determined by molecular absorption. Research the propagation characteristics at: VLF (submarine communication), HF (ionospheric reflection), microwave (satellite links), and optical frequencies. Why can’t we use 22 GHz or 183 GHz for satellite communication?
5. Multipath Fading and Diversity Techniques
Multipath propagation causes destructive interference (Rayleigh fading in urban environments). Modern systems use:
-
Frequency diversity: OFDM spreading data across multiple carriers
-
Spatial diversity: MIMO using multiple antennas
-
Polarization diversity: Exploiting orthogonal polarizations
-
Time diversity: Channel coding and interleaving
Study: How does the coherence bandwidth relate to delay spread? Why does urban mobile communication (~1-2 GHz) experience more severe multipath than rural?
-
-
Review of Transmission line theory. 20 Jan 2026 — Ch 2 of ME.
notesReview Questions: Transmission Lines, VSWR, and Telegrapher Equations
-
[Level 1] State the telegrapher’s equations for a transmission line. What do the terms R, L, G, and C represent physically?
Answer:
The telegrapher’s equations in the frequency domain are:
\[\frac{dV(z)}{dz} = -(R + j\omega L)I(z)\]\[\frac{dI(z)}{dz} = -(G + j\omega C)V(z)\]Where:
-
R = series resistance per unit length (Ω/m) - represents conductor losses
-
L = series inductance per unit length (H/m) - represents magnetic energy storage
-
G = shunt conductance per unit length (S/m) - represents dielectric losses
-
C = shunt capacitance per unit length (F/m) - represents electric energy storage
-
-
[Level 2] Derive the characteristic impedance \(Z_0\) of a transmission line. For a lossless line, express \(Z_0\) in terms of L and C.
Answer:
Starting from the telegrapher’s equations, we can derive that:
\[Z_0 = \sqrt{\frac{R + j\omega L}{G + j\omega C}}\]For a lossless line (R = 0, G = 0):
\[Z_0 = \sqrt{\frac{L}{C}}\]This is a real, frequency-independent value. For example:
-
Coaxial cable (RG-58): \(Z_0 = 50\ \Omega\)
-
Twin-lead: \(Z_0 = 300\ \Omega\)
-
Microstrip on FR4: \(Z_0\) typically \(50\text{-}100\ \Omega\)
-
-
[Level 2] What is VSWR (Voltage Standing Wave Ratio)? A transmission line has a load reflection coefficient \(\Gamma_L = 0.5\angle 60°\). Calculate the VSWR.
Answer:
VSWR is the ratio of maximum to minimum voltage magnitude on a transmission line with impedance mismatch:
\[\text{VSWR} = \frac{|V|_{max}}{|V|_{min}} = \frac{1 + |\Gamma_L|}{1 - |\Gamma_L|}\]Given \(\Gamma_L = 0.5\angle 60°\), we have \(|\Gamma_L| = 0.5\).
\[\text{VSWR} = \frac{1 + 0.5}{1 - 0.5} = \frac{1.5}{0.5} = 3\]This means the maximum voltage is 3 times the minimum voltage. A VSWR of 1 indicates perfect match (no reflections), while higher values indicate more mismatch.
-
[Level 3] A \(50\ \Omega\) transmission line of length \(\ell = \lambda/8\) is terminated with a load \(Z_L = 100 + j50\ \Omega\). Calculate the input impedance \(Z_{in}\) seen at the generator end.
Answer:
Using the transmission line impedance transformation equation:
\[Z_{in} = Z_0 \frac{Z_L + jZ_0\tan(\beta\ell)}{Z_0 + jZ_L\tan(\beta\ell)}\]With \(\ell = \lambda/8\), we have \(\beta\ell = 2\pi/\lambda \times \lambda/8 = \pi/4\), so \(\tan(\beta\ell) = \tan(\pi/4) = 1\).
Substituting \(Z_0 = 50\ \Omega\) and \(Z_L = 100 + j50\ \Omega\):
\[Z_{in} = 50 \frac{(100 + j50) + j50(1)}{50 + j(100 + j50)(1)}\]\[= 50 \frac{100 + j100}{50 + j100 - 50} = 50 \frac{100 + j100}{j100}\]\[= 50 \frac{100 + j100}{j100} = 50(1 - j) = 50 - j50\text{ Ω}\]The input impedance is \(50 - j50\ \Omega\) (\(50\ \Omega\) resistance with \(50\ \Omega\) capacitive reactance).
-
[Level 4] A lossless transmission line with \(Z_0 = 75\ \Omega\) operates at 2 GHz (\(\lambda = 15\) cm). A load \(Z_L = 150\ \Omega\) is connected. You need to match this load using a quarter-wave transformer. Calculate: (a) the characteristic impedance of the quarter-wave section, (b) the physical length of the matching section, and (c) the reflection coefficient at the input if the dielectric has \(\varepsilon_r = 2.25\).
Answer:
(a) Quarter-wave transformer impedance:
For quarter-wave matching:
\[Z_{QW} = \sqrt{Z_0 \times Z_L} = \sqrt{75 \times 150} = \sqrt{11250} \approx 106.1\text{ Ω}\](b) Physical length:
In a medium with \(\varepsilon_r = 2.25\), the wavelength is:
\[\lambda_g = \frac{\lambda_0}{\sqrt{\varepsilon_r}} = \frac{15\text{ cm}}{\sqrt{2.25}} = \frac{15}{1.5} = 10\text{ cm}\]The quarter-wave section length is:
\[\ell = \frac{\lambda_g}{4} = \frac{10}{4} = 2.5\text{ cm}\](c) Reflection coefficient at input:
With proper quarter-wave matching, the input impedance equals \(Z_0 = 75\ \Omega\), so the reflection coefficient at the input is:
\[\Gamma_{in} = \frac{Z_{in} - Z_0}{Z_{in} + Z_0} = \frac{75 - 75}{75 + 75} = 0\]Perfect match is achieved (at the design frequency).
Note: This matching is frequency-dependent and works perfectly only at 2 GHz and odd multiples of this frequency.
Exploration Topics: Historical Context & Modern Applications
1. Oliver Heaviside and the Telegrapher’s Equations (1880s)
Oliver Heaviside developed the telegrapher’s equations to analyze signal transmission on telegraph lines, introducing the concept of impedance and developing operational calculus (precursor to Laplace transforms). His work enabled long-distance telephony by showing that adding inductance (loading coils) could reduce distortion.
Research: What were "Pupin coils" and how did they revolutionize telephone networks? Why was Heaviside’s work initially rejected by the scientific establishment?
2. Transmission Lines in Modern High-Speed Digital Systems
Transmission line effects dominate when signal rise times are comparable to the propagation delay. For a 10 cm PCB trace with εr = 4.5, propagation delay is ~1 ns. Rise times in modern systems:
-
USB 2.0: ~2 ns (transmission line effects marginal)
-
USB 3.0: ~100 ps (critical transmission line design)
-
PCIe Gen 4: ~25 ps (extreme care needed)
-
DDR5 memory: ~50 ps
Investigate: What are the key differences between electrical length and physical length? How do vias and connectors affect signal integrity?
3. Coaxial Cables vs. Microstrip Lines
Two fundamental transmission line types with different trade-offs:
Coaxial cables:
-
Shielded, no radiation
-
Higher cost, difficult to integrate
-
Used in: RF test equipment, cable TV, antenna feeds
Microstrip lines:
-
Planar, easy to fabricate
-
Can radiate, especially at discontinuities
-
Used in: PCBs, integrated circuits, millimeter-wave systems
Explore: Why do cell phone PCBs use microstrip at GHz frequencies? What is the "critical frequency" where a trace becomes a transmission line?
4. Smith Chart: The Analog Computer for RF Engineers
Invented by Phillip Smith in 1939, the Smith chart is a graphical tool for solving transmission line problems without calculators. It represents complex impedances on the complex reflection coefficient plane.
Study: How does the Smith chart represent impedance matching? Why is it still used despite modern computational tools? Practice: Plot the impedance transformation for the quarter-wave example in Question 5.
5. Time-Domain Reflectometry (TDR)
TDR sends a fast pulse down a transmission line and observes reflections to diagnose faults:
-
Open circuit: positive reflection
-
Short circuit: negative reflection
-
Resistive load: partial reflection
-
Capacitive/inductive discontinuity: characteristic reflection shape
Modern applications:
-
Cable fault location (telecom, power)
-
PCB trace impedance verification
-
Soil moisture sensing (agriculture)
-
Radar and LIDAR systems
Research: How does a TDR distinguish between an open circuit at 10 m and a capacitive discontinuity at 10 m? What is the relationship between TDR and the S11 measurement on a vector network analyzer?
27 Jan 2026 — notes
Review Questions: Impedance Matching, Quarter-Wave Transformers, and Power Transfer
-
[Level 1] Why is impedance matching important in RF and microwave circuits? What happens to power when there is a mismatch?
Answer:
Impedance matching is critical for maximum power transfer from source to load. When there is a mismatch:
-
Reflected power = \(|\Gamma|^2 \times\) incident power
-
Transmitted power = \((1 - |\Gamma|^2) \times\) incident power
-
Standing waves form on the transmission line
-
Voltage and current maxima can damage components
-
In antenna systems, mismatch reduces radiated power and can affect radiation patterns
For maximum power transfer, the load impedance should equal the complex conjugate of the source impedance: \(Z_L = Z_S^*\).
Perfect match (\(\Gamma = 0\)) delivers 100% of available power to the load.
-
-
[Level 2] Explain the principle of a quarter-wave transformer. Why does it work only at specific frequencies?
Answer:
A quarter-wave transformer uses a transmission line section of length \(\lambda/4\) with characteristic impedance \(Z_{QW} = \sqrt{Z_0 Z_L}\) to match a load \(Z_L\) to a source with impedance \(Z_0\).
At the design frequency, the electrical length is 90°, and the input impedance becomes:
\[Z_{in} = Z_{QW} \frac{Z_L + jZ_{QW}\tan(90°)}{Z_{QW} + jZ_L\tan(90°)}\]Since \(\tan(90°) \to \infty\):
\[Z_{in} = \frac{Z_{QW}^2}{Z_L} = \frac{Z_0 Z_L}{Z_L} = Z_0\]Frequency dependence: The electrical length \(\beta\ell = 2\pi\ell/\lambda = 90°\) only at the design frequency. At other frequencies, \(\beta\ell \neq 90°\), \(\tan(\beta\ell) \neq \infty\), and perfect matching is lost.
The transformer provides good matching over a bandwidth of approximately 10-20% of the center frequency.
-
[Level 2] A source with \(Z_S = 50\ \Omega\) delivers power to a load \(Z_L = 100 + j75\ \Omega\) through a lossless transmission line with \(Z_0 = 50\ \Omega\). Calculate the reflection coefficient and the percentage of power reflected.
Answer:
The reflection coefficient at the load is:
\[\Gamma_L = \frac{Z_L - Z_0}{Z_L + Z_0} = \frac{(100 + j75) - 50}{(100 + j75) + 50} = \frac{50 + j75}{150 + j75}\]Converting to polar form:
Numerator: \(|50 + j75| = \sqrt{50^2 + 75^2} = \sqrt{2500 + 5625} = \sqrt{8125} \approx 90.14\)
Angle: \(\tan^{-1}(75/50) \approx 56.3°\)
Denominator: \(|150 + j75| = \sqrt{150^2 + 75^2} = \sqrt{22500 + 5625} = \sqrt{28125} \approx 167.7\)
Angle: \(\tan^{-1}(75/150) \approx 26.6°\)
\[\Gamma_L = \frac{90.14}{167.7}\angle(56.3° - 26.6°) \approx 0.537\angle29.7°\]Percentage of power reflected:
\[\text{Power reflected} = |\Gamma_L|^2 \times 100\% = (0.537)^2 \times 100\% \approx 28.8\%\]Therefore, approximately 28.8% of the power is reflected and 71.2% is delivered to the load.
-
[Level 3] Design a single-stub matching network to match a load \(Z_L = 60 + j80\ \Omega\) to a \(50\ \Omega\) line. The stub is a short-circuited line with \(Z_0 = 50\ \Omega\). Find the distance d from the load to the stub and the stub length \(\ell_{stub}\).
Answer:
Single-stub matching requires two steps:
Step 1: Find distance d where \(Y_{in}(d)\) has admittance with \(\text{Re}\{Y\} = Y_0 = 1/50 = 0.02\) S
First, normalize: \(y_L = Y_L/Y_0 = Z_0/Z_L = 50/(60 + j80)\)
\[y_L = \frac{50}{60 + j80} = \frac{50(60 - j80)}{(60 + j80)(60 - j80)} = \frac{3000 - j4000}{3600 + 6400} = \frac{3000 - j4000}{10000} = 0.3 - j0.4\]We need to move along the line until \(\text{Re}\{y\} = 1\). Using the transmission line equation or Smith chart, we find that we need to move approximately \(d \approx 0.132\lambda\) from the load toward the generator.
At this point, \(y(d) \approx 1 + j1.2\) (normalized admittance).
Step 2: Design stub to cancel imaginary part
The stub must provide susceptance \(b_{stub} = -1.2\) (normalized) to cancel the \(j1.2\).
A short-circuited stub has input admittance:
\[y_{stub} = -j\cot(\beta\ell_{stub})\]We need: \(-\cot(\beta\ell_{stub}) = -1.2\), so \(\cot(\beta\ell_{stub}) = 1.2\)
This gives: \(\beta\ell_{stub} = \cot^{-1}(1.2) \approx 0.694\) rad \(\approx 39.8°\)
Therefore: \(\ell_{stub} \approx 0.111\lambda\)
Final answer:
-
Stub position: \(d \approx 0.132\lambda\) from load
-
Stub length: \(\ell_{stub} \approx 0.111\lambda\) (short-circuited)
-
-
[Level 4] A \(50\ \Omega\) transmission line operates at 1 GHz (\(\lambda_0 = 30\) cm) and is terminated with a load \(Z_L = 75 + j50\ \Omega\). Calculate: (a) the load reflection coefficient \(\Gamma_L\), (b) the locations (in cm from the load) of the first voltage maximum and minimum, (c) the input impedance at a distance of \(\lambda/8\) from the load, and (d) if a transmitter delivers 20 W into this line, how much power is delivered to the load?
Answer:
(a) Load reflection coefficient:
\[\Gamma_L = \frac{Z_L - Z_0}{Z_L + Z_0} = \frac{(75 + j50) - 50}{(75 + j50) + 50} = \frac{25 + j50}{125 + j50}\]Converting to rectangular form by multiplying by complex conjugate:
\[\Gamma_L = \frac{(25 + j50)(125 - j50)}{(125 + j50)(125 - j50)} = \frac{3125 - j1250 + j6250 + 2500}{15625 + 2500} = \frac{5625 + j5000}{18125}\]\[\Gamma_L = 0.310 + j0.276\]In polar form: \(|\Gamma_L| = \sqrt{0.310^2 + 0.276^2} = \sqrt{0.096 + 0.076} = \sqrt{0.172} \approx\) 0.415
Phase: \(\theta_\Gamma = \tan^{-1}(0.276/0.310) \approx 41.7°\) or 0.727 rad
(b) Voltage maximum and minimum locations:
Voltage maxima occur at: \(z_{max} = -\lambda\theta_\Gamma/(4\pi) + n\lambda/2\)
First maximum: \(z_{max} = -30 \times 0.727/(4\pi) =\) -1.74 cm from load (toward generator)
Voltage minima occur at: \(z_{min} = -\lambda\theta_\Gamma/(4\pi) + \lambda/4 + n\lambda/2\)
First minimum: \(z_{min} = -1.74 + 7.5 =\) 5.76 cm from load
(c) Input impedance at \(\lambda/8\) from load:
Using the transmission line equation with \(\beta\ell = 2\pi(\lambda/8)/\lambda = \pi/4\):
\[Z_{in} = Z_0 \frac{Z_L + jZ_0\tan(\pi/4)}{Z_0 + jZ_L\tan(\pi/4)} = 50 \frac{(75+j50) + j50(1)}{50 + j(75+j50)(1)}\]\[= 50 \frac{75 + j100}{50 + j75 - 50} = 50 \frac{75 + j100}{j75} = 50 \frac{(75 + j100)(-j)}{75}\]\[= 50 \frac{100 - j75}{75} = 50(1.333 - j) = \textbf{66.7 - j50 Ω}\](d) Power delivered to load:
The power delivered to the load is:
\[P_L = P_{inc}(1 - |\Gamma_L|^2) = 20 \times (1 - 0.415^2) = 20 \times (1 - 0.172) = 20 \times 0.828 = \textbf{16.6 W}\]The reflected power is \(20 \times 0.172 = 3.4\) W.
Exploration Topics: Historical Context & Modern Applications
1. The Wilkinson Power Divider (1960)
Ernest Wilkinson invented the resistive power divider in 1960, providing a simple way to split RF power equally between two ports with:
-
Equal power division (3 dB to each port)
-
Matched impedances at all ports
-
Isolation between output ports
The key innovation: a quarter-wave transformer on each arm with a resistor between outputs. This elegant design is still ubiquitous in RF systems.
Research: How does the isolation resistor work? Why is the Wilkinson divider preferred over a simple T-junction? Design a 3-way Wilkinson divider.
2. Broadband Matching: From Fano to Modern UWB Systems
Robert Fano (1950) proved fundamental limits on matching bandwidth: you cannot achieve perfect match over infinite bandwidth with finite-complexity networks. The gain-bandwidth product is limited by the load Q-factor.
Modern broadband techniques:
-
Tapered transmission lines
-
Multi-section transformers (binomial, Chebyshev)
-
Resistive matching (trades efficiency for bandwidth)
-
Non-Foster matching (active, controversial)
Investigate: What is the Bode-Fano limit? How do ultra-wideband (UWB) antennas achieve 3-10 GHz bandwidth?
3. Tunable Matching Networks in Software-Defined Radio
Modern SDRs operate across wide frequency ranges (100 MHz - 6 GHz) and need dynamic impedance matching. Solutions include:
-
Switched capacitor/inductor banks
-
Varactor diodes (voltage-controlled capacitance)
-
RF MEMS switches
-
Tunable metamaterial structures
Key challenge: Tuning speed vs. power handling vs. insertion loss
Explore: How does the iPhone antenna tuner work across 30+ cellular bands? What are the trade-offs between electromechanical vs. solid-state tuning?
4. Impedance Matching in Biomedical Applications
Critical for wireless power transfer (WPT) to implantable devices:
-
Cochlear implants
-
Pacemakers with wireless charging
-
Brain-computer interfaces
-
Pill cameras
Challenge: Human tissue is lossy (high \(\varepsilon_r = 50\text{-}80\), conductivity \(\sigma = 0.5\text{-}2\) S/m), and the "load" impedance varies with patient movement, hydration, and tissue type.
Study: How is impedance matching achieved when the load changes dynamically? What frequencies are optimal for in-body power transfer?
5. Vector Network Analyzers and S-Parameters
Modern VNAs measure scattering parameters (S-parameters) to characterize RF components:
-
S11: input reflection (return loss)
-
S21: forward transmission (insertion loss)
-
S12: reverse transmission (isolation)
-
S22: output reflection
The VNA contains:
-
Directional couplers to separate incident/reflected waves
-
High-precision impedance standards (open, short, load) for calibration
-
Phase-coherent receivers
Research: What is de-embedding? How does SOLT (Short-Open-Load-Thru) calibration remove cable and fixture effects? Why are S-parameters preferred over Z-parameters at RF?
-
Advanced electromagnetics
-
Maxwell’s equations and boundary conditions, impedance boundary condition for good conductors. 02 Feb 2026 — Ch 1.5, 1.7, example 5.7 of AE, and extra notes on IBC.
notesReview Questions: Boundary Conditions, Skin Depth, and Impedance Boundary Condition
-
[Level 1] State the electromagnetic boundary conditions at the interface between two media. What happens to the tangential and normal components of \(\vec{E}\) and \(\vec{H}\)?
Answer:
At the interface between two media (labeled 1 and 2), the boundary conditions are:
Tangential components:
\[\hat{n} \times (\vec{E}_2 - \vec{E}_1) = 0 \quad \text{(tangential E continuous)}\]\[\hat{n} \times (\vec{H}_2 - \vec{H}_1) = \vec{J}_s \quad \text{(tangential H discontinuous by surface current)}\]Normal components:
\[\hat{n} \cdot (\vec{D}_2 - \vec{D}_1) = \rho_s \quad \text{(normal D discontinuous by surface charge)}\]\[\hat{n} \cdot (\vec{B}_2 - \vec{B}_1) = 0 \quad \text{(normal B continuous)}\]Where:
-
\(\hat{n}\) is the unit normal vector pointing from medium 1 to medium 2
-
\(\vec{J}_s\) is surface current density (A/m)
-
\(\rho_s\) is surface charge density (\(C/m^2\))
For perfect conductors, the tangential electric field is zero at the surface.
-
-
[Level 2] Derive the skin depth \(\delta_s\) for a good conductor. A copper sheet (\(\sigma = 5.8 \times 10^7\) S/m, \(\mu_r = 1\)) is used as shielding at 1 GHz. Calculate the skin depth.
Answer:
For a good conductor (\(\sigma \gg \omega\varepsilon\)), the electromagnetic wave decays exponentially as it penetrates the conductor:
\[\vec{E}(z) = \vec{E}_0 e^{-z/\delta_s} e^{-jz/\delta_s}\]The skin depth is:
\[\delta_s = \sqrt{\frac{2}{\omega\mu\sigma}} = \sqrt{\frac{1}{\pi f\mu\sigma}}\]For copper at 1 GHz:
\[\delta_s = \sqrt{\frac{1}{\pi \times 10^9 \times (4\pi \times 10^{-7}) \times (5.8 \times 10^7)}}\]\[= \sqrt{\frac{1}{\pi \times 10^9 \times 4\pi \times 10^{-7} \times 5.8 \times 10^7}} = \sqrt{\frac{1}{7.286 \times 10^{10}}}\]\[\delta_s \approx 2.1 \times 10^{-6}\text{ m} = 2.1\text{ μm}\]At 1 GHz, the field decays to 37% (1/e) of its surface value within only 2.1 micrometers of copper.
For effective shielding (>99% attenuation), use thickness \(\geq 3\delta_s \approx 6.3\) μm.
-
[Level 2] What is the impedance boundary condition (IBC)? Under what conditions is it valid, and what approximation does it provide?
Answer:
The Impedance Boundary Condition (IBC) is an approximate boundary condition for good conductors that relates the tangential electric and magnetic fields at the surface:
\[\hat{n} \times \vec{E}_{tan} = Z_s (\hat{n} \times \vec{H}_{tan}) \times \hat{n}\]Or more simply:
\[\vec{E}_{tan} = Z_s \vec{J}_s\]where the surface impedance is:
\[Z_s = \sqrt{\frac{j\omega\mu}{\sigma}} = \frac{1 + j}{\sigma\delta_s} = R_s + jX_s\]For a good conductor, \(R_s = X_s = 1/(\sigma\delta_s)\).
Validity conditions:
-
Good conductor: \(\sigma \gg \omega\varepsilon\)
-
Thickness \(\gg \delta_s\) (or infinitely thick)
-
Radius of curvature \(\gg \delta_s\) (locally flat)
Advantages:
-
Avoids solving fields inside conductor
-
Reduces 3D problem to 2D surface problem
-
Accurate for RF shielding, cavity resonators, and antenna ground planes
Applications: EMI/EMC analysis, cavity perturbation, radar cross-section of coated targets.
-
-
[Level 3] A plane wave with magnetic field amplitude \(H_0 = 1\) A/m at 10 GHz is incident normally on a thick aluminum sheet (\(\sigma = 3.5 \times 10^7\) S/m). Calculate: (a) the skin depth, (b) the surface impedance \(Z_s\), and (c) the tangential electric field at the surface.
Answer:
(a) Skin depth:
\[\delta_s = \sqrt{\frac{1}{\pi f\mu_0\sigma}} = \sqrt{\frac{1}{\pi \times 10^{10} \times 4\pi \times 10^{-7} \times 3.5 \times 10^7}}\]\[= \sqrt{\frac{1}{4.398 \times 10^{11}}} \approx 1.51 \times 10^{-6}\text{ m} = 1.51\text{ μm}\](b) Surface impedance:
\[Z_s = \frac{1 + j}{\sigma\delta_s} = \frac{1 + j}{(3.5 \times 10^7)(1.51 \times 10^{-6})}\]\[= \frac{1 + j}{52.85} = 0.0189(1 + j) = 0.0189 + j0.0189\text{ Ω}\]Or in polar form: \(|Z_s| = 0.0267\ \Omega, \angle 45°\)
Alternatively:
\[|Z_s| = \sqrt{\frac{\omega\mu_0}{\sigma}} = \sqrt{\frac{2\pi \times 10^{10} \times 4\pi \times 10^{-7}}{3.5 \times 10^7}} \approx 0.0267\text{ Ω}\](c) Tangential electric field:
Using the IBC: \(E_{tan} = Z_s H_{tan}\)
\[\vec{E}_{tan} = (0.0189 + j0.0189) \times 1 = 0.0189 + j0.0189\text{ V/m}\]Magnitude: \(|E_{tan}| \approx 0.0267\) V/m
This very small tangential electric field (compared to \(H_0 = 1\) A/m in free space, which would give \(E \approx 377\) V/m) confirms that aluminum is an excellent conductor at RF frequencies.
-
[Level 4] Calculate the shielding effectiveness (SE) of a 50 μm thick aluminum enclosure (\(\sigma = 3.5 \times 10^7\) S/m, \(\mu_r = 1\)) at 100 MHz. A plane wave with \(E_0 = 10\) V/m is incident normally on the shield. Find: (a) the skin depth at 100 MHz, (b) the ratio of thickness to skin depth (\(t/\delta_s\)), (c) the transmission coefficient magnitude \(|T|\), and (d) the shielding effectiveness in dB. Assume \(SE(dB) \approx 20\log_{10}(1/|T|)\) for good conductors when \(t \gg \delta_s\).
Answer:
(a) Skin depth at 100 MHz:
\[\delta_s = \sqrt{\frac{1}{\pi f\mu_0\sigma}} = \sqrt{\frac{1}{\pi \times 10^8 \times 4\pi \times 10^{-7} \times 3.5 \times 10^7}}\]\[= \sqrt{\frac{1}{4.398 \times 10^{10}}} = \sqrt{2.274 \times 10^{-11}} \approx 4.77 \times 10^{-6}\text{ m} = 4.77\text{ μm}\](b) Ratio of thickness to skin depth:
Given \(t = 50\) μm:
\[\frac{t}{\delta_s} = \frac{50}{4.77} \approx 10.5\]Since \(t \approx 10.5\delta_s\), the shield is thick enough that the "good shield" approximation applies.
(c) Transmission coefficient:
For a plane wave incident on a good conductor with \(t \gg \delta_s\), the transmission coefficient is approximately:
\[|T| \approx e^{-t/\delta_s} = e^{-10.5} \approx 2.75 \times 10^{-5}\]This means only about 0.00275% of the incident field penetrates through the shield.
(d) Shielding effectiveness:
The shielding effectiveness is:
\[SE = 20\log_{10}\left(\frac{1}{|T|}\right) = 20\log_{10}(e^{t/\delta_s}) = 20 \times \frac{t}{\delta_s} \times \log_{10}(e)\]\[= 20 \times 10.5 \times 0.434 = 91.1\text{ dB}\]Or using the simpler formula: \(SE \approx 8.686 \times (t/\delta_s)\)
\[SE = 8.686 \times 10.5 \approx 91.2\text{ dB}\]Physical interpretation:
-
The incident electric field \(E_0 = 10\) V/m is attenuated by 91 dB
-
The transmitted field is \(E_t = E_0 \times |T| = 10 \times 2.75 \times 10^{-5} = 2.75 \times 10^{-4}\) V/m = 0.275 mV/m
-
A 50 μm aluminum foil provides over 90 dB of shielding at 100 MHz
-
Note: This calculation ignores reflection losses at the boundaries, which would further increase SE
Practical note: In reality, shielding effectiveness is often limited by apertures (ventilation holes, seams, cable penetrations) rather than material thickness. A single 1 mm slot can reduce SE from 90 dB to 20-30 dB!
-
Exploration Topics: Historical Context & Modern Applications
1. The Discovery of Skin Effect (1883-1886)
Horace Lamb (1883) and Oliver Heaviside (1886) independently discovered that alternating current concentrates near the surface of conductors. This "skin effect" was initially a curiosity but became critical for:
-
Telephone line losses (motivating Heaviside’s work)
-
Transformer design at power frequencies
-
RF circuit design in the 20th century
Research: What is "proximity effect" and how does it differ from skin effect? How did early RF engineers compensate for skin effect before understanding the physics?
2. Litz Wire and High-Frequency Conductors
To mitigate skin effect losses, engineers developed specialized conductors:
Litz wire: Many thin, individually insulated strands twisted together
-
Each strand has diameter < δs
-
Strands transposed to equalize current
-
Used in: power converters (50-500 kHz), induction heating, MRI coils
Hollow conductors: Since current flows only in skin depth, why use solid wire?
-
Microwave tubes use copper tubing (weight/cost savings)
-
Coaxial cables use copper-clad aluminum or steel
Silver plating: Silver has σ = 6.3 × 107 S/m (9% better than copper)
-
Common on RF connectors and cavity resonators
-
Cost justified only where δs is critical
Investigate: At what frequency does a 1 mm copper wire have 50% more loss than DC? How thick should silver plating be at 10 GHz?
3. Electromagnetic Shielding and EMC
The IBC simplifies shielding effectiveness (SE) calculations:
\[SE(dB) = 20\log_{10}\left|\frac{E_{incident}}{E_{transmitted}}\right|\]For a good conductor of thickness t:
\[SE \approx 20\log_{10}(e^{t/\delta_s}) = 8.686 \times \frac{t}{\delta_s} \quad \text{dB}\]Plus reflection loss at the boundaries.
Modern challenges:
-
EMI from switching power supplies (harmonics to GHz)
-
Shielding for 5G base stations (massive MIMO)
-
Protecting medical implants from wireless power
Explore: What is the "shielding effectiveness" of a 0.1 mm aluminum foil at 2.4 GHz? Why do microwave oven doors have perforated metal screens?
4. Frequency-Selective Surfaces: Engineering Boundary Conditions
Frequency-selective surfaces (FSS) are periodic arrays of metallic patches or apertures that act as spatial filters, exploiting boundary conditions to control electromagnetic wave transmission and reflection.
Basic principle:
Unlike uniform conductors which reflect all frequencies, FSS can be designed to:
-
Reflect certain frequencies while transmitting others (bandpass/bandstop)
-
Create artificial magnetic conductors at specific frequencies
-
Provide polarization selectivity
Common FSS geometries:
-
Cross-dipole arrays: Bandstop filters (reflect resonant frequency)
-
Loop/slot arrays: Bandpass filters (transmit resonant frequency)
-
Jerusalem cross: Wider bandwidth, dual-polarized
-
Multilayer FSS: Sharper roll-off, multiple bands
Real-world applications:
Radome design for aircraft:
-
Protect radar antennas while being transparent at operating frequency
-
Block interference from other onboard systems
-
Example: F-35 fighter jet uses multilayer FSS in radome
Architectural electromagnetic shielding:
-
Allow WiFi/cellular (2-6 GHz) while blocking microwave ovens (2.4 GHz)
-
Energy-efficient windows (IR reflection, visible transmission)
Stealth technology:
-
Jaumann absorbers: multiple FSS layers with dielectric spacers
-
Reduces radar cross-section (RCS) at specific threat frequencies
Antenna reflectors:
-
Dichroic subreflectors in satellite antennas
-
Reflect one band (e.g., Ku) while transmitting another (Ka)
Explore: How is FSS periodicity related to operating wavelength? What happens when the angle of incidence changes? Why are fractal FSS geometries (Sierpinski, Koch) advantageous?
5. Superconducting RF Cavities
Below critical temperature Tc, superconductors have zero DC resistance, but AC losses persist:
Normal conductors at RF:
-
Rs ∝ √f (skin effect limited)
-
Q-factor ~ 104 for copper cavities
Superconductors (niobium, Tc = 9.2 K):
-
Rs ∝ f2 at low T (much smaller than normal)
-
Q-factor ~ 1010 achievable
-
Used in: particle accelerators (CERN LHC), quantum computers
Challenges:
-
Extreme cooling (liquid helium, 4.2 K or lower)
-
Surface preparation (nanometer-scale cleanliness)
-
Multipactor breakdown (electron avalanche)
Study: Why does RF resistance in superconductors increase as f2 instead of √f? What limits the maximum accelerating gradient in SRF cavities?
-
-
Vector potentials as a means of solving Maxwell’s equation, definition of Green’s function. 03 Feb 2026 — Ch 6.1-5 of AE, example 6.1 of AE (homework), Ch 15.1-2 of AE.
notesReview Questions: Vector Potentials and Green’s Functions
-
[Level 1] Why do we introduce vector potentials \(\vec{A}\) and scalar potential \(\phi\)? How are they related to the electric and magnetic fields?
Answer:
Answer: Vector and scalar potentials are introduced to simplify solving Maxwell’s equations. Instead of solving for six field components (\(\vec{E}\) and \(\vec{H}\), each with 3 components), we solve for four potential components (\(\vec{A}\) has 3 components, \(\phi\) has 1).
The relationships are:
\[\vec{B} = \nabla \times \vec{A}\]\[\vec{E} = -\nabla\phi - \frac{\partial\vec{A}}{\partial t} \quad \text{(time domain)}\]In the phasor domain:
\[\vec{E} = -\nabla\phi - j\omega\vec{A}\]Advantages:
-
Automatically satisfies \(\nabla \cdot \vec{B} = 0\) (since divergence of a curl is zero)
-
Reduces coupled equations to wave equations for \(\vec{A}\) and \(\phi\)
-
Gauge freedom allows additional simplification (Coulomb or Lorenz gauge)
-
Natural formulation for radiation problems
-
-
[Level 2] State the wave equation for the magnetic vector potential \(\vec{A}\) in the Lorenz gauge. What is the source term?
Answer:
Answer: In the Lorenz gauge, defined by:
\[\nabla \cdot \vec{A} + j\omega\mu\varepsilon\phi = 0 \quad \text{(phasor domain)}\]The wave equation for \(\vec{A}\) becomes:
\[\nabla^2\vec{A} + k^2\vec{A} = -\mu\vec{J}\]where \(k^2 = \omega^2\mu\varepsilon\) is the wavenumber squared.
The source term is \(-\mu\vec{J}\), where \(\vec{J}\) is the current density (\(A/m^2\)).
Similarly, the scalar potential satisfies:
\[\nabla^2\phi + k^2\phi = -\frac{\rho}{\varepsilon}\]where \(\rho\) is the charge density (\(C/m^3\)).
Key insight: These are inhomogeneous Helmholtz equations - the same mathematical form as the wave equation with sources. The solution uses Green’s functions.
-
[Level 2] What is a Green’s function? Give the mathematical definition and explain its physical significance.
Answer:
Answer: A Green’s function \(G(\vec{r}, \vec{r}')\) is the response at position \(\vec{r}\) due to a unit point source at position \(\vec{r}'\). It satisfies:
\[\nabla^2 G(\vec{r}, \vec{r}') + k^2 G(\vec{r}, \vec{r}') = -\delta(\vec{r} - \vec{r}')\]where \(\delta(\vec{r} - \vec{r}')\) is the Dirac delta function.
Physical significance:
The Green’s function represents the field (or potential) at an observation point due to an impulse source. It is the electromagnetic equivalent of an impulse response in linear systems theory.
Solution for arbitrary source:
Given a source distribution \(\vec{J}(\vec{r}')\), the vector potential is:
\[\vec{A}(\vec{r}) = \mu \int_V \vec{J}(\vec{r}') G(\vec{r}, \vec{r}') dV'\]This convolution integral is the foundation of antenna radiation calculations. The Green’s function for free space is:
\[G(\vec{r}, \vec{r}') = \frac{e^{-jk|\vec{r} - \vec{r}'|}}{4\pi|\vec{r} - \vec{r}'|}\]representing outward-propagating spherical waves.
Exploration Topics: Historical Context & Modern Applications
1. George Green and the Birth of Potential Theory (1828)
George Green, a self-taught miller’s son, published "An Essay on the Application of Mathematical Analysis to the Theories of Electricity and Magnetism" in 1828, introducing:
-
Green’s functions (named after him posthumously)
-
Green’s theorem (fundamental in vector calculus)
-
Potential theory as a unifying framework
His work went unnoticed for 20 years until William Thomson (Lord Kelvin) discovered it. Green died young at 49, never knowing his profound impact.
Research: What was Green’s original physical insight about potential functions? How did his miller occupation influence his mathematical thinking about energy?
2. Machine Learning and Computational Electromagnetics
Recent trend: replacing expensive EM simulations with ML models.
Surrogate modeling:
-
Train neural network on simulation data
-
Large speedup for antenna optimization
-
Example: Predict S-parameters from geometry
Inverse design:
-
Specify desired radiation pattern
-
ML finds antenna geometry
-
Topology optimization + deep learning
Physics-informed neural networks (PINNs):
-
Embed Maxwell’s equations in loss function
-
Combine data + physics
-
Reduce training data requirements
Challenges:
-
Generalization beyond training domain
-
Physical realizability constraints
-
Interpretability vs. black-box models
Research: What is "adjoint variable method" in EM optimization? How does it compare to ML approaches? Can generative AI (diffusion models) design antennas?
Future directions:
-
Digital twins of EM environments (6G network planning)
-
Real-time RCS computation for autonomous vehicles
-
Quantum computing for large-scale EM problems (BQP vs. NP)
-
-
Green’s function for 1D electromagnetics problems, 09 Feb 2026 — Ch 15.1-2,6 of AE.
notesReview Questions: One-Dimensional Green’s Functions
-
[Level 1] What is a Green’s function \(g(x,x')\)? Explain its analogy to the impulse response in linear time-invariant (LTI) systems.
Answer:
A Green’s function \(g(x,x')\) is the response (potential or field) at observation point \(x\) due to a unit point source located at \(x'\). It satisfies the differential equation:
\[\frac{d^2g(x,x')}{dx^2} + k_0^2 g(x,x') = -\delta(x-x')\]where \(\delta(x-x')\) is the Dirac delta function representing a unit impulse source.
Analogy to LTI systems:
Just as the impulse response \(h(t)\) of an LTI system represents the output due to an impulse input \(\delta(t)\), the Green’s function represents the electromagnetic response to a point source. The solution for an arbitrary source distribution \(f(x')\) can be obtained by convolution:
\[\phi(x) = \int_{-\infty}^{\infty} f(x') g(x,x') dx'\]This is directly analogous to the convolution integral \(y(t) = \int h(t-\tau)x(\tau)d\tau\) in LTI systems theory.
Physical interpretation: The Green’s function is the fundamental building block for solving electromagnetic problems. Once we know \(g(x,x')\), we can solve for any source distribution by superposition.
-
[Level 1] State the defining equation for the one-dimensional Green’s function \(g(x,x')\). What is the source term, and why is it called a "unit" source?
Answer:
The defining equation is:
\[\frac{d^2g(x,x')}{dx^2} + k_0^2 g(x,x') = -\delta(x-x')\]where: - \(k_0 = \omega\sqrt{\mu\varepsilon}\) is the wavenumber of the medium - \(\delta(x-x')\) is the Dirac delta function
The source term \(\delta(x-x')\) is called a "unit" source because it has the property:
\[\int_{-\infty}^{\infty} \delta(x-x') dx = 1\]The delta function is zero everywhere except at \(x = x'\), where it is infinite, but its integral equals unity. This represents an idealized point source with unit strength located at position \(x'\).
When we have a distributed source \(f(x')\), the solution is obtained by integrating the Green’s function weighted by the source distribution—essentially summing up contributions from infinitesimal unit sources at each point.
-
[Level 2] In the Fourier transform approach to deriving \(g(x,x')\), we obtain the expression:
\[g(x,x') = \frac{1}{2\pi}\int_{-\infty}^{\infty} \frac{e^{jk(x-x')}}{k^2 - k_0^2} dk\]Why is this integral problematic? What are the "poles," and where are they located?
Answer:
This integral is problematic because the denominator \(k^2 - k_0^2 = (k-k_0)(k+k_0)\) becomes zero at \(k = \pm k_0\). These points are called poles of the integrand.
Location of poles: - First pole at \(k = +k_0\) - Second pole at \(k = -k_0\)
At these values, the integrand becomes infinite, making the standard integral undefined. We cannot simply evaluate this integral using elementary techniques.
Physical significance:
The poles correspond to the natural oscillation frequencies (wavenumbers) of the homogeneous system. The presence of poles indicates that the system can support propagating wave solutions at wavenumber \(k_0\) in both positive and negative directions.
-
[Level 2] The final form of the 1D Green’s function is:
\[g(x,x') = \frac{-j}{2k_0}\exp(-jk_0|x-x'|)\]Provide a physical interpretation of this expression. What does it represent when combined with the time-harmonic factor \(e^{j\omega t}\)?
Answer:
Mathematical structure:
The expression has three key components:
-
Amplitude factor: \(-j/(2k_0)\) sets the overall scale
-
Absolute value: \(|x-x'|\) represents the distance from source to observation point
-
Phase factor: \(\exp(-jk_0|x-x'|)\) contains the spatial oscillation
Physical interpretation:
When we include the time-harmonic factor \(e^{j\omega t}\), the complete space-time dependence is:
\[g(x,x',t) = \frac{-j}{2k_0}\exp(j\omega t - jk_0|x-x'|)\]This represents: - Outward-propagating waves traveling away from the source at \(x = x'\) - Waves propagate in both directions (positive and negative \(x\)) along the line - The amplitude is constant with distance (characteristic of 1D)—no geometric spreading in 1D
Traveling wave:
For \(x > x'\), the phase is \(\omega t - k_0(x-x')\), representing a wave traveling in the \(+x\) direction with phase velocity \(v_p = \omega/k_0\).
For \(x < x'\), the phase is \(\omega t - k_0(x'-x)\), representing a wave traveling in the \(-x\) direction.
Why no amplitude decay?
Unlike 3D (\(1/r\)) or 2D (\(1/\sqrt{r}\)), the 1D Green’s function has no geometric spreading factor. In 1D, energy cannot spread in transverse directions—it only propagates along the line, maintaining constant amplitude.
Applications:
This 1D solution is relevant for: - Leaky-wave antennas (uniform line sources) - One-dimensional antenna arrays (in the far-field, perpendicular to the array axis) - Beamforming analysis
-
-
[Level 4] Verify by direct substitution that the derived Green’s function \(g(x,x') = (-j/2k_0)\exp(-jk_0|x-x'|)\) satisfies the defining equation:
\[\frac{d^2g}{dx^2} + k_0^2 g = -\delta(x-x')\]Consider the regions \(x > x'\) and \(x < x'\) separately, and explain how the delta function emerges at \(x = x'\).
Answer:
For \(x \neq x'\):
Case 1: \(x > x'\), so \(|x-x'| = x-x'\):
\[g(x,x') = \frac{-j}{2k_0}e^{-jk_0(x-x')}\]First derivative:
\[\frac{dg}{dx} = \frac{-j}{2k_0}(-jk_0)e^{-jk_0(x-x')} = \frac{-1}{2}e^{-jk_0(x-x')}\]Second derivative:
\[\frac{d^2g}{dx^2} = \frac{-1}{2}(-jk_0)e^{-jk_0(x-x')} = \frac{jk_0}{2}e^{-jk_0(x-x')}\]Thus:
\[\frac{d^2g}{dx^2} + k_0^2 g = \frac{jk_0}{2}e^{-jk_0(x-x')} + k_0^2\left(\frac{-j}{2k_0}e^{-jk_0(x-x')}\right)\]\[= \frac{jk_0}{2}e^{-jk_0(x-x')} - \frac{jk_0}{2}e^{-jk_0(x-x')} = 0 \quad \checkmark\]Case 2: \(x < x'\), so \(|x-x'| = x'-x\):
\[g(x,x') = \frac{-j}{2k_0}e^{-jk_0(x'-x)}\]First derivative:
\[\frac{dg}{dx} = \frac{-j}{2k_0}(jk_0)e^{-jk_0(x'-x)} = \frac{1}{2}e^{-jk_0(x'-x)}\]Second derivative:
\[\frac{d^2g}{dx^2} = \frac{1}{2}(jk_0)e^{-jk_0(x'-x)} = \frac{jk_0}{2}e^{-jk_0(x'-x)}\]Thus:
\[\frac{d^2g}{dx^2} + k_0^2 g = \frac{jk_0}{2}e^{-jk_0(x'-x)} + k_0^2\left(\frac{-j}{2k_0}e^{-jk_0(x'-x)}\right) = 0 \quad \checkmark\]For \(x = x'\) (emergence of delta function):
The homogeneous equation is satisfied everywhere except at \(x = x'\). The delta function emerges from the discontinuity in the first derivative.
From property (4), we showed:
\[\left.\frac{dg}{dx}\right|_{x=x'^+} - \left.\frac{dg}{dx}\right|_{x=x'^-} = -1\]This jump discontinuity in \(dg/dx\) means that \(d^2g/dx^2\) contains a delta function:
Summary:
The Green’s function satisfies: - The homogeneous equation for \(x \neq x'\) - The full inhomogeneous equation including the delta function source when we account for the derivative discontinuity at \(x = x'\)
This behavior is characteristic of all Green’s functions: smooth away from the source, with a singularity (or derivative discontinuity in 1D) at the source location.
Exploration Topics: Historical Context & Modern Applications
1. Line Sources and Cylindrical Waves: The Physical Reality of 1D Green’s Functions
While the 1D Green’s function may seem like a mathematical abstraction, it describes real physical systems involving infinite line sources—sources that extend indefinitely along one direction.
Physical examples of line sources:
-
Infinite wire antennas: Vertical monopoles above ground plane (image theory creates effective line source)
-
Lightning channels: ~5 km vertical current channel approximates line source for ground-level observers
-
Power transmission lines: Under faults, behave as radiating line sources
-
Plasma columns: Gas discharge tubes, lightning simulators, Z-pinch devices
Cylindrical wave propagation:
Unlike the 1D Green’s function (constant amplitude), a true infinite line source in 3D space radiates cylindrical waves:
\[G_{\text{line}}(\rho) = \frac{1}{4j}H_0^{(2)}(k_0\rho) \approx \sqrt{\frac{2}{\pi k_0\rho}}e^{-jk_0\rho} \quad (\rho \gg \lambda)\]where \(\rho\) is radial distance from the line and \(H_0^{(2)}\) is the Hankel function of second kind.
Relationship to 1D case:
The 1D Green’s function \(g(x,x') = -j/(2k_0) \exp(-jk_0|x-x'|)\) describes propagation along the line, while cylindrical waves describe radiation away from the line. Both are needed for a complete description.
Practical applications:
-
Cellular base station antennas: Vertical arrays approximate line sources for horizontal coverage
-
Ground-penetrating radar: Line-source approximation for shallow targets
-
Ionospheric propagation: Lightning-radiated VLF waves couple into Earth-ionosphere waveguide
-
Microwave heating: Linear slot arrays in industrial microwave ovens
Historical note:
Arnold Sommerfeld’s 1909 solution for a vertical dipole above a lossy ground plane required evaluating the Sommerfeld integral—essentially integrating the 1D Green’s function over all possible plane-wave components. This problem remained challenging for decades and motivated development of asymptotic methods.
Research: What is the "Norton surface wave" for vertical antennas over ground? How does it differ from the direct radiation? At what distance does the \(1/\rho\) cylindrical spreading transition to \(1/r^2\) spherical spreading for finite-length line sources?
2. Leaky-Wave Antennas: 1D Green’s Functions in Action
Leaky-wave antennas exploit the 1D Green’s function physics—a guided wave that continuously "leaks" radiation along its length, behaving like a continuous line source.
Basic principle:
-
Slow wave structure (periodic or inhomogeneous)
-
Wave travels along the structure with β < k₀ (fast wave)
-
Continuously radiates at angle θ = arcsin(β/k₀)
-
Beam angle varies with frequency (frequency scanning)
Historical development:
-
1940s: First leaky-wave antennas (W.W. Hansen at Stanford)
-
1950s-60s: Slotted waveguides for radar (Arthur Oliner’s work)
-
1980s: Microstrip leaky-wave antennas
-
2000s: Metamaterial-based designs (CRLH structures)
-
2020s: Terahertz and mm-wave applications for 6G
Modern applications:
-
Automotive radar (77 GHz): Frequency-scanning for object detection
-
Satellite communications: Lightweight, high-gain antennas
-
Millimeter-wave 5G/6G: Beam-steering without phase shifters
-
Through-wall imaging: Security and rescue operations
Why 1D Green’s function matters:
The radiation pattern of a leaky-wave antenna is computed by integrating the 1D Green’s function (the response to a point source) along the antenna length, weighted by the leakage rate α(z):
\[E(\theta) \propto \int_0^L e^{-\alpha z} g_{\text{1D}}(z) e^{-jk_0 z \sin\theta} dz\]This convolution determines the beam pattern and scanning properties.
Explore: What is a composite right/left-handed (CRLH) leaky-wave antenna? How does it achieve backward-to-forward beam scanning? Why are metamaterials useful for leaky-wave designs?
3. The Fourier Transform and the Birth of Signal Processing
The Fourier transform technique used to derive the 1D Green’s function has an epic history connecting pure mathematics, physics, and engineering.
Historical timeline:
-
1807: Joseph Fourier proposes that any periodic function can be expanded as a sum of sines and cosines (heat equation)
-
1822: "Théorie analytique de la chaleur" published—mathematical community skeptical
-
1860s: Acceptance after Riemann’s work on trigonometric series
-
1920s: Norbert Wiener and others extend to Fourier integrals for non-periodic functions
-
1960s: Cooley-Tukey FFT algorithm revolutionizes computation
-
Present: Foundation of all digital signal processing
The controversy:
Fourier’s claim that "any" function could be represented by sines and cosines seemed absurd to contemporaries (Lagrange, Laplace). The notion of convergence for discontinuous functions wasn’t rigorous until 50 years later.
Modern perspective:
The Fourier transform is actually a unitary operator on L²(ℝ)—it’s an isomorphism between time and frequency domains. Parseval’s theorem shows it preserves energy, making it fundamental to:
-
Signal processing (filtering, modulation, spectral analysis)
-
Quantum mechanics (position ↔ momentum)
-
Electromagnetics (time ↔ frequency, space ↔ wavenumber)
-
Image processing (JPEG compression uses discrete cosine transform)
Why the pole treatment matters:
The "low-loss medium" trick (k₀ → k₀ - jα) elegantly enforces causality through analytic continuation. This connects to:
-
Kramers-Kronig relations: Causality constraints on permittivity
-
Hilbert transforms: Signal processing (analytic signals)
-
Dispersion relations: Fundamental physics constraints
Research: What is the "uncertainty principle" for Fourier transforms? How does it relate to Heisenberg’s quantum uncertainty? What are "distributions" (generalized functions) and why did Laurent Schwartz win the Fields Medal for formalizing them?
4. Method of Moments: Numerical Green’s Functions
When analytical Green’s functions are unavailable (complex geometries, inhomogeneous media), numerical methods use the same conceptual framework.
Method of Moments (MoM):
Roger Harrington’s 1968 book "Field Computation by Moment Methods" established the standard approach:
-
Express unknown currents as weighted basis functions: \(J(r') = \sum_n I_n f_n(r')\)
-
Use Green’s function to relate currents to fields
-
Enforce boundary conditions → matrix equation
-
Solve for weights \(I_n\)
Key advantages:
-
Integral equation (not differential): Only discretize surfaces/wires, not all space
-
Exact boundary conditions on conductors
-
Green’s function automatically includes radiation condition
Modern developments:
-
Fast multipole method (FMM): Reduces O(N²) to O(N log N) complexity
-
Adaptive cross approximation (ACA): Compresses MoM matrices
-
GPU acceleration: Parallel matrix-vector products for iterative solvers
-
Machine learning: Learn compressed representations of Green’s functions
Applications:
-
FEKO, CST, HFSS: Commercial EM simulation tools
-
Antenna design: From cell phones to satellite dishes
-
EMC/EMI analysis: Circuit board radiation, cable coupling
-
Radar cross-section: Stealth aircraft design
Explore: What is the "fast multipole method"? How does it achieve O(N log N) complexity? What’s the difference between MoM and finite element method (FEM)?
-
-
Green’s function for 2 and 3D electromagnetics problems. 10 Feb 2026 — Ch 15.1-2,6 of AE.
notes, Extra notes on constants-derivationReview Questions: Two-Dimensional and Three-Dimensional Green’s Functions
-
[Level 1] When deriving the 2D Green’s function, why is the cylindrical coordinate system \((r,\theta)\) preferred over Cartesian coordinates \((x,y)\)? What symmetry argument allows us to simplify the problem?
Answer:
The cylindrical coordinate system is preferred because when we place the source point \(\vec{r}'\) at the origin, the problem exhibits cylindrical symmetry—the field depends only on the radial distance \(r\) from the source, not on the angle \(\theta\).
Key observations:
-
A point source at the origin radiates equally in all directions in the 2D plane
-
Therefore, \(g(r,\theta) = g(r)\) with no \(\theta\) dependence
-
This simplifies the Laplacian from \(\nabla^2 = \frac{1}{r}\frac{\partial}{\partial r}\left(r\frac{\partial}{\partial r}\right) + \frac{1}{r^2}\frac{\partial^2}{\partial\theta^2}\) to just \(\nabla^2 = \frac{1}{r}\frac{\partial}{\partial r}\left(r\frac{\partial}{\partial r}\right)\)
In Cartesian coordinates:
There is no natural symmetry to exploit—we would have to deal with both \(x\) and \(y\) dependence, making the problem much more complicated.
Physical analogy:
Just as dropping a pebble in a pond creates circular ripples (not elliptical or irregular patterns), a point source in 2D creates cylindrically symmetric waves.
-
-
[Level 2] What is the Sommerfeld radiation boundary condition? Write its mathematical form for the 2D case and explain its physical significance.
Answer:
The Sommerfeld radiation boundary condition (RBC) is a constraint that ensures the Green’s function represents outward-propagating waves at infinity, corresponding to radiation away from the source.
Mathematical form (2D):
+
\[\lim_{r \to \infty} \sqrt{r}\left(\frac{\partial g}{\partial r} + jk g\right) = 0\]+ for \(e^{j\omega t}\) time convention.
Physical significance:
-
Enforces causality: waves propagate away from the source, not toward it
-
Eliminates incoming waves from infinity (which would be non-physical)
-
Selects the appropriate solution from the set of possible solutions
Application to 2D Green’s function:
The general homogeneous solution is \(g(r) = a H_0^{(1)}(kr) + b H_0^{(2)}(kr)\), where:
-
\(H_0^{(1)}(kr)\) represents incoming cylindrical waves (as \(r \to \infty\))
-
\(H_0^{(2)}(kr)\) represents outgoing cylindrical waves
The RBC requires \(a = 0\), leaving only \(H_0^{(2)}(kr)\), which satisfies:
+
\[H_0^{(2)}(kr) \sim \sqrt{\frac{2}{\pi kr}} e^{-j(kr - \pi/4)} \quad \text{as } r \to \infty\]Historical note:
Arnold Sommerfeld introduced this boundary condition in 1912 while solving electromagnetic wave propagation problems. It’s essential for uniquely determining solutions to radiation problems.
-
-
[Level 2] The 2D Green’s function involves Bessel functions \(J_\alpha(x)\) and \(Y_\alpha(x)\), or equivalently Hankel functions \(H_\alpha^{(1)}(x)\) and \(H_\alpha^{(2)}(x)\). Explain why Hankel functions are preferred over Bessel functions for the Green’s function solution.
Answer:
Hankel functions are preferred because they directly represent propagating waves (either incoming or outgoing), while Bessel functions represent standing waves.
Mathematical relationship:
+
\[H_\alpha^{(1)}(x) = J_\alpha(x) + j Y_\alpha(x)\]+
\[H_\alpha^{(2)}(x) = J_\alpha(x) - j Y_\alpha(x)\]Asymptotic behavior as \(x \to \infty\):
-
\(J_\alpha(x) \sim \sqrt{\frac{2}{\pi x}} \cos\left(x - \frac{\alpha\pi}{2} - \frac{\pi}{4}\right)\) — oscillatory (standing wave)
-
\(Y_\alpha(x) \sim \sqrt{\frac{2}{\pi x}} \sin\left(x - \frac{\alpha\pi}{2} - \frac{\pi}{4}\right)\) — oscillatory (standing wave)
-
\(H_\alpha^{(1)}(x) \sim \sqrt{\frac{2}{\pi x}} e^{+j(x - \alpha\pi/2 - \pi/4)}\) — incoming wave
-
\(H_\alpha^{(2)}(x) \sim \sqrt{\frac{2}{\pi x}} e^{-j(x - \alpha\pi/2 - \pi/4)}\) — outgoing wave
Why this matters:
Using Bessel functions \(J_\alpha\) and \(Y_\alpha\), we would write:
+
\[g(r) = a J_0(kr) + b Y_0(kr)\]This is a standing wave solution (superposition of incoming and outgoing waves), which doesn’t naturally satisfy the radiation boundary condition.
Using Hankel functions, we write:
+
\[g(r) = a H_0^{(1)}(kr) + b H_0^{(2)}(kr)\]Each term explicitly represents a traveling wave (incoming or outgoing). The Sommerfeld RBC immediately tells us \(a = 0\) (no incoming waves), giving the clean solution:
+
\[g(r) = b H_0^{(2)}(kr)\]Analogy:
It’s like choosing between: - Bessel functions: describing waves as \(\cos(kx)\) and \(\sin(kx)\) (standing waves) - Hankel functions: describing waves as \(e^{+jkx}\) and \(e^{-jkx}\) (traveling waves)
For radiation problems, traveling wave representation is more natural.
-
-
[Level 3] Compare the amplitude decay behavior of 1D, 2D, and 3D Green’s functions as a function of distance from the source. Explain the physical reason for the different decay rates.
Answer:
The three Green’s functions exhibit different amplitude decay rates due to geometric spreading in different dimensions.
Summary of Green’s functions:
-
1D: \(g(x,x') = \frac{-j}{2k_0} e^{-jk_0|x-x'|}\)
-
2D: \(g(r,r') = \frac{-j}{4} H_0^{(2)}(k|\vec{r}-\vec{r}'|) \sim \frac{1}{\sqrt{r}} e^{-jkr}\) (far field)
-
3D: \(g(r,r') = \frac{1}{4\pi} \frac{e^{-jk|\vec{r}-\vec{r}'|}}{|\vec{r}-\vec{r}'|} \sim \frac{1}{r} e^{-jkr}\)
Amplitude decay:
-
1D: No decay — amplitude is constant with distance
-
2D: \(1/\sqrt{r}\) decay — cylindrical spreading
-
3D: \(1/r\) decay — spherical spreading
Physical explanation:
The decay rate is determined by how energy spreads geometrically in each dimension:
1D (no decay): - Energy propagates along a line - No transverse spreading possible - Power flux density remains constant - Think of a plane wave propagating in one direction
2D (\(1/\sqrt{r}\) decay): - Energy spreads over cylindrical surfaces of circumference \(2\pi r\) - Power must be conserved: \(P = \text{intensity} \times \text{circumference}\) - If power is constant, then \(\text{intensity} \propto 1/r\) - Field amplitude \(\propto \sqrt{\text{intensity}} \propto 1/\sqrt{r}\) - Think of ripples on a pond
3D (\(1/r\) decay): - Energy spreads over spherical surfaces of area \(4\pi r^2\) - Power conservation: \(P = \text{intensity} \times \text{area}\) - If power is constant, then \(\text{intensity} \propto 1/r^2\) - Field amplitude \(\propto \sqrt{\text{intensity}} \propto 1/r\) - Think of a light bulb radiating in all directions
Energy conservation perspective:
Consider a source radiating power \(P\):
-
1D: All power flows in one direction → intensity constant
-
2D: Power spreads over circle of radius \(r\) → intensity \(\propto 1/r\)
-
3D: Power spreads over sphere of radius \(r\) → intensity \(\propto 1/r^2\)
Since field amplitude \(\propto \sqrt{\text{intensity}}\), we get the respective decay rates.
Practical implications:
-
1D: Communication along transmission lines (no path loss due to spreading)
-
2D: Ground wave propagation (cylindrical spreading from vertical antenna)
-
3D: Free space propagation (spherical spreading, Friis transmission formula)
-
-
[Level 3] The lecture notes state that 1D needs "an infinite sheet of current," 2D needs "an infinite line of current," and 3D needs "a tiny point of current." Explain what this means and why different dimensions require different physical current configurations.
Answer:
This statement refers to the physical realization of the delta function source in each dimension and connects to how the Green’s function is actually generated.
Mathematical context:
The Green’s function satisfies:
+
\[\nabla^2 g + k_0^2 g = -\delta(\vec{r} - \vec{r}')\]The right-hand side is a point source in the respective dimension, but what creates such a source in a real electromagnetic system?
1D Green’s function — Infinite sheet of current:
-
The 1D problem assumes variation only in one direction (say, \(x\))
-
To create a delta function source at \(x = x'\), we need:
-
Uniform current distribution in the \(y-z\) plane at \(x = x'\)
-
Infinite extent in \(y\) and \(z\) directions
-
This creates a field that varies only with \(x\)
-
Example: Infinite planar current sheet \(J_s \delta(x-x')\)
Physical realization: Approximated by large metal plates or ground planes in transmission line problems
2D Green’s function — Infinite line of current:
-
The 2D problem assumes variation in a plane (say, \(x-y\))
-
To create a delta function source at \((x',y')\), we need:
-
Line current along the \(z\)-axis at position \((x',y')\)
-
Infinite extent in the \(z\) direction
-
This creates cylindrically symmetric waves in the \(x-y\) plane
-
Example: Infinite vertical wire carrying current \(I \delta(x-x')\delta(y-y')\)
Physical realization: Approximated by tall vertical monopole antennas over ground planes
3D Green’s function — Tiny point of current:
-
The 3D problem has variation in all three dimensions
-
The source is a true point source at \(\vec{r}'\)
-
This is a localized current element: \(I \vec{dl} \delta(\vec{r} - \vec{r}')\)
-
This creates spherically symmetric waves
Physical realization: Small dipole antennas, Hertzian dipoles
Why different configurations?
The dimensionality of the problem determines which symmetries can be exploited:
-
1D: We exploit translational symmetry in \(y\) and \(z\) → need uniform source in those directions
-
2D: We exploit translational symmetry in \(z\) → need uniform source along \(z\)
-
3D: No translational symmetry → localized point source
Connection to antenna theory:
The vector potential due to current distribution \(\vec{J}(\vec{r}')\) is:
+
\[\vec{A}(\vec{r}) = \mu \int_V \vec{J}(\vec{r}') g(\vec{r}, \vec{r}') dV'\]For different antenna configurations: - Planar array: Integrate 3D Green’s function over a sheet → approximate 1D behavior in far field perpendicular to sheet - Linear array: Integrate 3D Green’s function over a line → approximate 2D behavior in plane perpendicular to line - Single element: 3D Green’s function directly applicable
Practical note:
In reality, we cannot build infinite structures, but the approximations work when: - The observation point is far from the edges - The extent is much larger than wavelength - We’re in the "near-field" region relative to the overall structure size
-
Exploration Topics: Historical Context & Modern Applications
1. Bessel and Hankel: The Mathematics of Cylindrical Waves
Friedrich Bessel (1784-1846) first derived Bessel functions in 1817 while studying planetary perturbations—specifically, the motion of planets under gravitational influence. He had no idea his functions would become fundamental to electromagnetic wave theory a century later.
Historical development:
-
1817: Bessel develops Bessel functions for celestial mechanics
-
1867: Lord Rayleigh uses Bessel functions to solve acoustic wave problems (vibrating membranes, drums)
-
1888: Hermann Hankel introduces Hankel functions as complex combinations of Bessel functions
-
1890s: Oliver Heaviside and others apply Bessel functions to electromagnetic wave propagation in cylindrical geometries
Why Hankel functions matter for electromagnetics:
Hankel saw that \(J_\alpha(x)\) and \(Y_\alpha(x)\) (real functions) represent standing waves, while their complex combinations \(H_\alpha^{(1)} = J_\alpha + jY_\alpha\) and \(H_\alpha^{(2)} = J_\alpha - jY_\alpha\) naturally represent traveling waves—perfect for radiation problems.
This was a profound insight: the same way \(e^{jkx}\) is more natural than \(\cos(kx)\) and \(\sin(kx)\) for traveling waves in 1D, Hankel functions are more natural than Bessel functions for cylindrical waves.
Modern applications:
-
Optical fibers: Mode propagation in cylindrical waveguides
-
Circular antenna arrays: Pattern synthesis and beamforming
-
Scattering from cylinders: Radar cross-section calculations
-
Acoustic imaging: Ultrasound beamforming and sonar
-
Seismology: Wave propagation in layered earth models
Computational challenges:
Bessel and Hankel functions are transcendental—they cannot be expressed in terms of elementary functions. For large arguments (\(x \gg 1\)), asymptotic expansions work well. For small arguments (\(x \approx 0\)), series expansions are used. Modern libraries (MATLAB, Python scipy.special) use sophisticated algorithms combining both approaches.
Research: What is the "Bessel function of the first kind of fractional order"? How are Bessel functions computed numerically (recurrence relations, continued fractions)? What is the connection between Bessel functions and Fourier-Bessel series?
2. Arnold Sommerfeld and the Radiation Condition (1912)
Arnold Sommerfeld (1868-1951) was one of the giants of theoretical physics, contributing to quantum mechanics, atomic theory, and electromagnetic wave propagation. His radiation boundary condition, introduced in 1912, solved a fundamental problem in electromagnetic theory.
The problem:
When solving wave equations in unbounded domains (infinite space), the differential equation alone has infinitely many solutions. How do we select the physically correct one representing radiation (outward-propagating waves)?
Sommerfeld’s insight:
For a source at the origin radiating in 3D, as \(r \to \infty\), the field must behave like an outward-propagating spherical wave:
+
\[g(r) \sim \frac{e^{-jkr}}{r}\]This implies:
+
\[\lim_{r \to \infty} r\left(\frac{\partial g}{\partial r} + jk g\right) = 0\]This condition uniquely selects the outgoing wave solution and eliminates non-physical incoming waves from infinity.
Extension to 2D:
For cylindrical waves, Sommerfeld showed the condition becomes:
+
\[\lim_{r \to \infty} \sqrt{r}\left(\frac{\partial g}{\partial r} + jk g\right) = 0\]with the \(\sqrt{r}\) factor reflecting cylindrical (not spherical) spreading.
Impact:
Sommerfeld’s radiation condition became the foundation for: - Antenna theory (Schelkunoff, Silver, Balanis) - Scattering theory (Mie scattering, radar cross-sections) - Perfectly Matched Layers (PML) in computational electromagnetics - Absorbing boundary conditions in FDTD simulations
Sommerfeld’s legacy:
Beyond the radiation condition, Sommerfeld supervised or influenced an extraordinary group of physicists: Werner Heisenberg, Wolfgang Pauli, Peter Debye, Hans Bethe, and many others. His 1949 lecture notes "Partial Differential Equations in Physics" remain a classic.
Explore: What is the "Silver-Müller radiation condition" and how does it differ from Sommerfeld’s? How are radiation boundary conditions implemented numerically in finite element or finite difference methods?
3. Cylindrical Antennas and the 2D Green’s Function
The 2D Green’s function \(g = -(j/4)H_0^{(2)}(kr)\) describes cylindrical wave propagation—the fundamental building block for analyzing cylindrical antennas and arrays.
Infinite wire antennas:
An infinitely long wire carrying uniform current \(I\) creates a field:
+
\[E_z(r) = -j\omega\mu I \times \frac{-j}{4}H_0^{(2)}(k_0 r)\]This is exactly the 2D Green’s function multiplied by the source strength \(-j\omega\mu I\).
Finite cylindrical antennas:
Real antennas have finite length \(L\). The field is obtained by integrating the 2D Green’s function over the antenna length with the current distribution \(I(z')\):
+
\[\vec{E}(\vec{r}) = -j\omega\mu \int_{-L/2}^{L/2} I(z') G_{2D}(\rho) e^{-jk_z(z-z')} dz'\]where \(\rho = \sqrt{x^2 + y^2}\) is the radial distance from the antenna axis.
Applications:
-
Monopole antennas over ground plane: Quarter-wave (\(\lambda/4\)) or half-wave (\(\lambda/2\)) monopoles
-
Dipole antennas: Half-wave dipoles, broadcast antennas
-
Slot antennas in cylinders: Aircraft and missile antennas
-
Helical antennas: Circular polarization for satellite communications
Cylindrical array antennas:
Arranging elements on a cylinder (rather than a line or plane) enables: - 360° azimuthal coverage - Electronic beam steering in azimuth - Applications: 5G base stations, radar, direction finding
The array pattern involves summing 2D Green’s functions from each element position.
Computational methods:
-
Method of Moments (MoM) for wire antennas
-
FEKO, NEC-2, NEC-4 (Numerical Electromagnetics Code)
-
Fast algorithms: Fast Multipole Method (FMM) accelerates summation of cylindrical waves
Research: What is the "near field" vs. "far field" transition for cylindrical waves? How does the Hankel function asymptotic form connect to far-field antenna patterns?
4. Special Functions in Computational Electromagnetics
Bessel and Hankel functions are just the tip of the iceberg. Electromagnetic problems across different geometries require various special functions:
Coordinate systems and their special functions:
-
Cartesian (x,y,z): Trigonometric functions (\(e^{jkx}\), \(\sin(kx)\), \(\cos(kx)\))
-
Cylindrical (r,θ,z): Bessel functions \(J_n\), \(Y_n\), Hankel functions \(H_n^{(1,2)}\)
-
Spherical (r,θ,φ): Spherical Bessel functions \(j_n\), \(y_n\), spherical Hankel functions \(h_n^{(1,2)}\), Legendre polynomials \(P_n\), associated Legendre functions \(P_n^m\)
-
Elliptical: Mathieu functions
-
Prolate/oblate spheroidal: Spheroidal wave functions
Why so many functions?
Each special function arises from separation of variables in the Helmholtz equation \(\nabla^2\psi + k^2\psi = 0\) in a particular coordinate system. The boundary conditions and geometry determine which function set is natural.
Numerical computation challenges:
-
Recurrence relations: \(J_{n+1}(x) = \frac{2n}{x}J_n(x) - J_{n-1}(x)\) (stable forward for small \(n\), unstable for large \(n\))
-
Asymptotic expansions: Work well for \(x \gg n\) but fail for \(x < n\)
-
Series expansions: Converge slowly for large arguments
-
Continued fractions: Alternative evaluation method
Modern libraries (MATLAB besselj, Python scipy.special.jv) use Miller’s algorithm (backward recurrence) and other sophisticated techniques.
Software tools:
-
MATLAB Symbolic Math Toolbox
-
Python: scipy.special (wraps C library AMOS)
-
Boost C++ library: special functions
-
GNU Scientific Library (GSL)
-
Mathematica, Maple: symbolic and numeric evaluation
Machine learning for special functions:
Recent research explores using neural networks to approximate special functions: - Faster evaluation than traditional methods - Difficult for exotic parameter ranges or high precision - Active area of research
Study: What is "catastrophic cancellation" in computing Bessel functions? How does Miller’s backward recurrence algorithm work? What are "Bessel function zeros" and why are they important for waveguide problems?
5. From 2D to 3D: The Physics of Dimensional Crossover
The transition from 2D to 3D wave propagation reveals fundamental physics about how dimension affects wave behavior.
Power conservation and spreading:
Consider a source radiating power \(P\):
-
2D: Power flows through cylindrical surface \(2\pi r h\) (height \(h\))
-
Intensity: \(I = P/(2\pi r h) \propto 1/r\)
-
Field amplitude: \(E \propto \sqrt{I} \propto 1/\sqrt{r}\)
-
Green’s function: \(g_{2D} \sim 1/\sqrt{r}\) (far field)
-
3D: Power flows through spherical surface \(4\pi r^2\)
-
Intensity: \(I = P/(4\pi r^2) \propto 1/r^2\)
-
Field amplitude: \(E \propto \sqrt{I} \propto 1/r\)
-
Green’s function: \(g_{3D} \sim 1/r\)
Dimensional crossover in real antennas:
A finite linear antenna of length \(L\) exhibits dimensional crossover:
-
Near field (\(r \ll L\)): Locally looks like infinite line source → 2D behavior (\(1/\sqrt{r}\))
-
Far field (\(r \gg L\)): Looks like point source → 3D behavior (\(1/r\))
The transition occurs around \(r \sim L\).
Applications:
Fresnel vs. Fraunhofer regions:
-
Fresnel zone (near field): \(r < 2D^2/\lambda\) where \(D\) is antenna size
-
Fraunhofer zone (far field): \(r > 2D^2/\lambda\)
The transition reflects dimensional crossover from extended source to point source.
Metamaterials and effective dimensionality:
Some metamaterial structures confine waves to effectively lower dimensions: - Surface plasmons: 3D light → 2D surface waves - Photonic crystals: Create effective 1D or 2D wave propagation in 3D structures
Quantum analogs:
Similar dimensional effects appear in quantum systems: - 2D electron gas in semiconductors (quantum wells) - 1D quantum wires - 0D quantum dots - Different density of states: \(\rho(E) \propto E^{(d-2)/2}\) where \(d\) is dimension
Research: What is the "radiation resistance" of a dipole antenna and how does it change with length? How do 2D materials like graphene support electromagnetic surface waves? What is the connection between the Green’s function singularity and the dimension of space?
-
-
Fields of a Hertz dipole. 16 Feb 2026 — Ch 4.2 of AT or Ch 6.6,6.7 of AE.
notes -
Duality principles, uniqueness theorem. 17 Feb 2026 — Ch 7.1-3 of AE.
notes
Evaluation
-
Course assignments (individual) [20]
-
Assignment #1 — released 12 Feb, due 23 Feb 2026
-
-
Course project (group of 2) [25]
-
Midsem exam [20] — date Sunday 01 March 2026, 10a - 1p.
-
Endsem exam [35]
Course outline
-
Broad course contents, with a focus on RF
-
Advanced principles in electromagnetics
-
Antennas
-
Antenna arrays
-
Metasurfaces
-
-
Prerequisites
-
Any UG/PG course on electromagnetics
-
Familiarity with programming
-
-
References:
-
[ME] Microwave Engineering, David Pozar, 4th ed., Wiley
-
[AE] Advanced Engineering Electromagnetics, Constantine Balanis, 3rd ed., Wiley
-
[AT] Antenna Theory & Applications, Constantine Balanis, 4th ed., Wiley
-
Detailed syllabus
This is an exhaustive list and all topics might not be covered.
Review content
-
Review of Maxwell’s equations, boundary conditions, phasor notation, plane wave propagation in free space and dielectric media, polarization, and reflection from interfaces.
-
Review of transmission line equations, impedance transformations, quarter wave transformations, matching techniques, coaxial and microstrip lines, rectangular waveguides, wave velocities and dispersion.
Advanced electromagnetics
-
Auxiliary vector potentials, solution of wave equations, near and far field radiation equations.
-
Electromagnetic theorems: duality, uniqueness, images, reciprocity, reaction, surface and volume equivalence, induction.
-
Green’s functions: 2/3D scalar forms for free space.
Antennas
-
Fields of a Hertz dipole antenna
-
Antenna parameters: radiation pattern, intensity, beamwidth, directivity, efficiency, gain, polarization, impedance, effective area, Friis equation, implications of reciprocity theorem for antennas.
-
Antennas: linear/loop, aperture antennas and connection with Fourier theory, horn antennas, microstrip patch antennas, broadband antennas, matching techniques.
Microwave network analysis
-
Concept of impedance, impedance/admittance matrices, scattering/ABCD matrices, signal flow graphs, excitation of waveguides.
Antenna arrays
-
Basic idea of beam forming and scanning by arraying, concept of array factor, linear and planar arrays, mutual coupling in arrays, arrays and feed networks
-
Introduction to Floquet Modes in Infinite Arrays
Metasurfaces
-
Design and analysis of periodic sub-wavelength structures for: changing surface impedance, controlling reflection/transmission phase, manipulating surface wave propagation, creating bandgap structures.
-
Examples of reconfigurable metasurfaces, anomalous reflectors, leaky wave antennas.
Back to Home